AD640BD 查看數據表（PDF） - Analog Devices
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AD640BD Datasheet PDF : 16 Pages
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AD640
IOUT = 50 µA (InputdBV + 60)
Equation (5)
Alternatively, for a sinusoidal input measured in dBm (power in
dB above 1 mW in a 50 Ω system) the output can be written
IOUT = 50 µA (InputdBm + 44)
Equation (6)
because the intercept for a sine wave expressed in volts rms is at
1.414 mV (from Table I) or –44 dBm.
OPERATION OF A SINGLE AD640
Figure 24 shows the basic connections for a single device, using
100 Ω load resistors. Output A is a negative going voltage with a
slope of –100 mV per decade; output B is positive going with a
slope of +100 mV per decade. For applications where absolute
calibration of the intercept is essential, the main output (from
LOG OUT, Pin 14) should be used; the LOG COM output can
then be grounded. To evaluate the demodulation response, a
simple low-pass output filter having a time constant of roughly
500 µs (3 dB corner of 320 Hz) is provided by a 4.7 µF (–20%
+80%) ceramic capacitor (Erie type RPE117-Z5U-475-K50V)
placed across the load. A DVM may be used to measure the
averaged output in verification tests. The voltage compliance at
Pins 13 and 14 extends from 0.3 V below ground up to 1 V
below +VS. Since the current into Pin 14 is from –0.2 mA at
zero signal to +2.3 mA when fully limited (dc input of >300 mV)
the output never drops below –230 mV. On the other hand, the
current out of Pin 13 ranges from 0.2 mA to +2.3 mA, and if
desired, a load resistor of up to 2 kΩ can be used on this output;
the slope would then be 2 V per decade. Use of the LOG COM
output in this way provides a numerically correct decibel read-
ing on a DVM (+100 mV = +1.00 dB).
Board layout is very important. The AD640 has both high gain
and wide bandwidth; therefore every signal path must be very
carefully considered. A high quality ground plane is essential,
but it should not be assumed that it behaves as an equipotential
plane. Even though the application may only call for modest
bandwidth, each of the three differential signal interface pairs
(SIG IN, Pins 1 and 20, SIG OUT, Pins 10 and 11, and LOG,
Pins 13 and 14) must have their own “starred” ground points to
avoid oscillation at low signal levels (where the gain is highest).
Unused pins (excluding Pins 8, 10 and 11) such as the attenua-
tor and applications resistors should be grounded close to the
package edge. BL1 (Pin 6) and BL2 (Pin 9) are internal bias
lines a volt or two above the –VS node; access is provided solely
for the addition of decoupling capacitors, which should be con-
nected exactly as shown (not all of them connect to the ground).
Use low impedance ceramic 0.1 µF capacitors (for example,
Erie RPE113-Z5U-105-K50V). Ferrite beads may be used
instead of supply decoupling resistors in cases where the supply
voltage is low.
Active Current-to-Voltage Conversion
The compliance at LOG OUT limits the available output volt-
age swing. The output of the AD640 may be converted to a
larger, buffered output voltage by the addition of an operational
amplifier connected as a current-to-voltage (transresistance)
stage, as shown in Figure 21. Using a 2 kΩ feedback resistor
(R2) the 50 µA/dB output at LOG OUT is converted to a volt-
age having a slope of +100 mV/dB, that is, 2 V per decade. This
output ranges from roughly –0.4 V for zero signal inputs to the
AD640, crosses zero at a dc input of precisely +1 mV (or
–1 mV) and is +4 V for a dc input of 100 mV. A passive
prefilter, formed by R1 and C1, minimizes the high frequency
energy conveyed to the op amp. The corner frequency is here
shown as 10 MHz. The AD844 is recommended for this appli-
cation because of its excellent performance in transresistance
modes. Its bandwidth of 35 MHz (with the 2 kΩ feedback resis-
tor) will exceed the baseband response of the system in most
applications. For lower bandwidth applications other op amps
and multipole active filters may be substituted (see, for example,
Figure 32 in the APPLICATIONS section).
Effect of Frequency on Calibration
The slope and intercept of the AD640 are calibrated during
manufacture using a 2 kHz square wave input. Calibration de-
pends on the gain of each stage being 10 dB. When the input
frequency is an appreciable fraction of the 350 MHz bandwidth
of the amplifier stages, their gain becomes imprecise and the
logarithmic slope and intercept are no longer fully calibrated.
However, the AD640 can provide very stable operation at fre-
quencies up to about one half the 3 dB frequency of the ampli-
fier stages. Figure 10 shows the averaged output current versus
input level at 30 MHz, 60 MHz, 90 MHz and 120 MHz. Fig-
ure 11 shows the absolute error in the response at 60 MHz and
at temperatures of –55°C, +25°C and +125°C. Figure 12 shows
the variation in the slope current, and Figure 13 shows the
variation in the intercept level (sinusoidal input) versus frequency.
If absolute calibration is essential, or some other value of slope
or intercept is required, there will usually be some point in the
user’s system at which an adjustment may be easily introduced.
For example, the 5% slope deficit at 30 MHz (see Figure 12)
may be restored by a 5% increase in the value of the load resis-
tor in the passive loading scheme shown in Figure 24, or by
inserting a trim potentiometer of 100 Ω in series with the feed-
back resistor in the scheme shown in Figure 21. The intercept
SIGNAL
INPUT
DENOTES A SHORT, DIRECT CONNECTION
TO THE GROUND PLANE.
ALL UNMARKED CAPACITORS ARE
0.1F CERAMIC (SEE TEXT)
10⍀
+5V
OPTIONAL
TERMINATION
RESISTOR
NC
20 19 18 17 16 15 14 13 12 11
SIG ATN CKT RG1 RG0 RG2 LOG LOG +VS SIG
+IN OUT COM
OUT COM
+OUT
1k⍀ 1k⍀
4.7F
RLA
100⍀
0.1%
4.7F
AD640
SIG ATN ATN ATN ATN
SIG
–IN LO COM COM IN BL1 –VS ITC BL2 –OUT
1
2
3
4
5
6
7
8
9 10
NC
NC
OPTIONAL
OFFSET BALANCE
RESISTOR
4.7⍀
–5V
NC = NO CONNECT
Figure 24. Connections for a Single AD640 to Verify Basic Performance
OUTPUT A
OUTPUT B
RLB
100⍀
0.1%
REV. C
–11–
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