AD797BN 查看數據表（PDF） - Analog Devices
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AD797BN Datasheet PDF : 16 Pages
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AD797
BYPASSING CONSIDERATIONS
To take full advantage of the very wide bandwidth and dynamic
range capabilities of the AD797 requires some precautions.
First, multiple bypassing is recommended in any precision
application. A 1.0 µF–4.7 µF tantalum in parallel with 0.1 µF
ceramic bypass capacitors are sufficient in most applications.
When driving heavy loads a larger demand is placed on the sup-
ply bypassing. In this case selective use of larger values of tanta-
lum capacitors and damping of their lead inductance with small
value (1.1 Ω to 4.7 Ω) carbon resistors can be an improvement.
Figure 32 summarizes bypassing recommendations. The symbol
(**) is used throughout this data sheet to represent the parallel
combination of a 0.1 µF and a 4.7 µF capacitor.
follower. Operation on 5 volt supplies allows the use of a 100 Ω
or less feedback network (R1 + R2). Since the AD797 shows
no unusual behavior when operating near its maximum rated
current, it is suitable for driving the AD600/AD602 (Figure 47)
while preserving their low noise performance.
Optimum flatness and stability at noise gains >1 sometimes
requires a small capacitor (CL) connected across the feedback
resistor (R1, Figure 35). Table II includes recommended values
of CL for several gains. In general, when R2 is greater than
100 Ω and CL is greater than 33 pF, a 100 Ω resistor should
be placed in series with CL. Source resistance matching is
assumed, and the AD797 should never be operated with unbal-
anced source resistance >200 kΩ/G.
0.1µF
VS
4.7µF
OR
KELVIN RETURN
0.1µF
VS
4.7 – 22.0µF
1.1 – 4.7Ω
KELVIN RETURN
USE SHORT
LEAD LENGTHS
(<5mm)
LOAD
CURRENT
USE SHORT
LEAD RETURNS
(<5mm)
LOAD
CURRENT
Figure 32. Recommended Power Supply Bypassing
THE NONINVERTING CONFIGURATION
Ultralow noise requires very low values of rBB’ (the internal
parasitic resistance) for the input transistors (≈6 Ω). This im-
plies very little damping of input and output reactive interac-
tions. With the AD797, additional input series damping is
required for stability with direct input to output feedback. A
100 Ω resistor in the inverting input (Figure 33) is sufficient;
the 100 Ω balancing resistor (R2) is recommended, but is not
required for stability. The noise penalty is minimal (eNtotal
≈2.1 nV/√Hz), which is usually insignificant. Best response
flatness is obtained with the addition of a small capacitor
(CL < 33 pF) in parallel with the 100 Ω resistor (Figure 34).
The input source resistance and capacitance will also affect the
response slightly and experimentation may be necessary for best
results.
R1
100Ω
+VS
**
2
7
R2
AD797 6
100Ω
VIN
3
4
**
RL
600Ω
VOUT
–VS
** USE POWER SUPPLY BYPASSING SHOWN IN FIGURE 32.
Figure 33. Voltage Follower Connection
Low noise preamplification is usually done in the noninverting
mode (Figure 35). For lowest noise the equivalent resistance of
the feedback network should be as low as possible. The 30 mA
minimum drive current of the AD797 makes it easier to achieve
this. The feedback resistors can be made as low as possible with
due consideration to load drive and power consumption. Table
II gives some representative values for the AD797 as a low noise
CL
100 Ω
+VS
**
RS*
VIN
CS*
2
7
AD797 6
3
4
**
–VS
VOUT
600 Ω
* SEE TEXT
** USE POWER SUPPLY BYPASSING SHOWN IN FIGURE 32.
Figure 34. Alternative Voltage Follower Connection
CL
R2
R1
VIN
+VS
**
2
7
AD797 6
3
4
**
VOUT
RL
–VS
** USE POWER SUPPLY BYPASSING SHOWN IN FIGURE 32.
Figure 35. Low Noise Preamplifier
Table II. Values for Follower With Gain Circuit
Gain
2
2
10
20
>35
R1
1 kΩ
300 Ω
33.2 Ω
16.5 Ω
10 Ω
R2
CL
1 kΩ
≈20 pF
300 Ω
≈10 pF
300 Ω
≈5 pF
316 Ω
(G–1) • 10 Ω
Noise
(Excluding rS)
3.0 nV/√Hz
1.8 nV/√Hz
1.2 nV/√Hz
1.0 nV/√Hz
0.98 nV/√Hz
The I-to-V converter is a special case of the follower configura-
tion. When the AD797 is used in an I-to-V converter, for in-
stance as a DAC buffer, the circuit of Figure 36 should be used.
The value of CL depends on the DAC and again, if CL is
–10–
REV. C
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